IPS101 Datasheet by Microsemi PoE Ltd.

[[[[

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

–

R

RE

EV

VI

IS

SI

IO

ON

N

1

10

0

-

INTRODUCTION

DESCRIPTION

The IN-PLUG

®

IPS101 is a special line-side

switching controller which provides simple yet high

performance active power factor correction. The

IPS101 was optimized for electronic ballast compact

SMPSs up to 300W that requires a minimum board

area, reduced component count and high efficiency.

The PFC forces the SMPS to draw a current

proportional to the instant AC line voltage in order to

charge a storage capacitor thus resulting in excellent

power factor and low line harmonics generation.

The output of the PFC is a regulated voltage which

slightly exceeds the peak line voltage and is generally

too high to be used as is. This is why a PFC is usually

followed by a DC/DC converter, providing one or

more isolated output(s) at the required voltage(s).

AAI offers the following solutions for the DC/DC

converter:

• Flyback converters (see IPS10 series)

• Push-pull converters (see IPS201 controller)

Other ICs and discrete solutions can be used as well.

More and more countries already impose PFC above

75W or soon will enforce this obligation.

In addition to the compliance with power factor and

line harmonics regulations, using a PFC offers other

advantages like:

• Reducing the utility bill by making the actual

power drawn from the line almost equal to the

apparent power paid to the utility company

• Allowing to draw more power from the wall

outlet or line circuit breaker without exceeding

the limits set by UL or other safety agencies.

FEATURES

•

Simple and easy to use.

•

High efficiency over 96% (in optimized designs)

•

Minimum external component count for lowest

cost.

•

3-input current-mode multiplier ensures

outstanding performance at any line voltage and

any load.

•

Under voltage protection.

•

Voltage error amplifier with provision for loop

stability compensation.

•

Cycle to cycle current limiting.

•

Thermal shut-down.

•

Capable of driving a broad range of power

MOSFETs.

•

Self oscillating at frequencies up to 300KHz

APPLICATIONS

•

SMPS.

•

Electronic ballast.

PIN CONFIGURATION: DIP-8 / SOIC-8

ORDERING INFORMATION

IN-PLUG® series: I

IP

PS

S1

10

01

1

Low Cost, High Efficiency

Power Factor Correction Controller

DRIVEVDCFBK

ISENSE

VCC

PKCAP

VAC

OPOUT

GND

IPS101

1

45

8

Part No. ROHS /

Pb-Free

Package Temperature Range

IPS101C-D -G-LF 8-Pin PDIP 0°C to +70°CCommercial

IPS101I-D -G-LF 8-Pin PDIP -40°C to +85°CIndustrial

IPS101C-SO -G-LF 8-Pin SOIC 0°C to +70°CCommercial

IPS101I-SO -G-LF 8-Pin SOIC -40°C to +85°CIndustrial

For detailed ordering information, see page 14

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

BASIC APPLICATION SCHEMATIC

Figure 1

BASIC APPLICATION WITH DC/DC FEED-BACK CONTROL

Figure 2

Note: This diagram displays a double feedback control. The resistor bridge R3/R4 can be set to safely guarantee a maximum

output voltage while the feedback control signal from the DC/DC block throught the optocoupler would manage the output

voltage regulation.

+

C4

L1

Q1

D1

PFC Controller

R7

R2

R6

PFC GND

C3

R3 R1

R9

C1

31

4 2

BR1

R4

AC IN

DC OUT

VCC

1

VDCFBK

2

COMPV

3

RMSCAP

4

VAC 8

DRIVE 7

ISENSE 6

GND 5

U1

IPS101

T1

CMC

C5

C2

CHIP SUPPLY

LOAD

+

C5

L1

Q1

D1

PFC Controller

R7R2

R6

PFC GND

C3

R3 R1

R9

C1

31

4 2

BR1

R4

DC OUT

VCC

1

VDCFBK

2

COMPV

3

RMSCAP

4

VAC 8

DRIVE 7

ISENSE 6

GND 5

U1

IPS101

T1

CMC

C4

C2

CHIP SUPPLY

U2

OPTOCOUPLER

AC IN

DC/DC

CONVERTER

C6

VY

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

FUNCTIONAL BLOCK DIAGRAM

Figure 3

PIN DESCRIPTION

Number Name Description

1 VCC IC supply pin.

The circuit contains a shunt regulator that behaves like a 10V zener. During start-up the IC

draws very little current. Operations start when the “zener” value is reached and stop should

the VCC voltage becomes less than approximately 8V.

2 VDCFBK Voltage feedback input pin.

Negative feedback of the voltage error amplifier which positive input is internally

connected to a 2.06V trimmed reference. It is used to regulate the voltage across the storage

output capacitor to a value slightly above the maximum line peak voltage.

3COMPV

Voltage loop compensation pin.

This is the output of the voltage error amplifier and is used for loop feedback

compensation purposes. Also used as an optional feedback loop to regulate the output of a

DC/DC converter fed by the PFC controller (see Fig. 2)

4 RMSCAP RMS capacitor pin.

The capacitor connected between this pin & GND generates a current proportional to the

RMS value of the AC line voltage which feeds the multiplier circuit to maintain the loop

gain constant at different line voltages thus preventing loop instabilities which could occur

with other arrangements.

5GND

Ground pin. This pin must be connected to the PFC module ground.

6ISENSE

Inductor current sensing pin.

This pin is used to measure the current flowing through the inductor which is forced by the

PFC controller to be proportional to the instant AC line voltage. The power MOSFET is

automatically driven in a self-oscillating mode to restart a new cycle when the current in the

inductor has dropped below half of its peak value.

7 DRIVE MOSFET gate drive pin.

The internal buffer connected to this pin can drive a broad variety of power MOSFETs

and IGBTs. A series resistor is sometimes added to improve the EMI signature.

8 VAC AC voltage pin.

This pin is used to sense the instantaneous AC line voltage through a series resistor that

performs a voltage to current conversion. The resulting current feeds the multiplier in order

to force the peak current in the inductor to be proportional to the instant AC line voltage.

REF

V

DCFBK RMSCAP

GND DRIVEISENSE

IPS101

BANDGAP

REGULATOR

TRIMMED

VCC

V

AC

COMPV

3

5

_

+

VOLTAGE

ERROR

AMPLIFIER

241

678

MULTIPLIER

CONVERTERS

V to I RMS

&

INTERNAL

BIAS

IN T. BIAS

_

+

_

+

VOFF

VON

CONTROL

LOGIC

DRIVER

ON

OFF

MIRROR

I

ERROR

I

RMS

I

AC

IN 1 IN2

IN 3

OUT

2.18V

Undervoltage lockout

3-inEut current multiEIier: Voltage error amEIifier: MOSFET current control:

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

INTRODUCTION:

Without PFC, most SMPS simply rectify the AC voltage to charge a relatively large capacitor. This results in huge

spikes drawn from the line which generates harmonics and degrades the power factor to 0.5 – 0.7.

With the IPS101, the power factor exceeds 0.95 and the harmonic distortion could be less than 5%. The IPS101 is

also a very efficient pre-regulator that charges a storage capacitor at an adjustable regulated DC voltage. This feature

can be used to build very high-efficiency and low-cost isolated SMPS featuring single or multiple outputs in the

range of 50-500W.

OPERATING DESCRIPTION:

3-input current multiplier:

The heart of the IPS101 PFC controller is a 3-input current-mode multiplier. This multiplier is key in monitoring a

constant loop gain that is the only way to ensure a good stability and response over a broad range of input AC

voltages and output loads.

The first multiplier input is fed by I

AC

, a current proportional to the instant AC line voltage. This information is used

to force the current drawn from the AC line to be proportional to the instant line voltage thus resulting in a power

factor close to unity. The SMPS then behaves like a resistive load whith an impedance that varies according to the

RMS line voltage and the load thanks to the other action of the two multiplier inputs.

As shown in Fig. 1, a resistor (R1) connected between V

AC

(pin 8) and the rectified AC line voltage, performs the V

to I conversion that generates I

AC.

The value of R1 is usually 1 MΩ.

The second multiplier input is fed by I

RMS

, a current proportional to the AC line RMS value. This current is derived

from I

AC

by a dedicated RMS converter using only a non-critical external capacitor (C1).

The value of C1 is usually 1 uF for 50 / 60Hz operations. A much lower value would result in a more harmonic

distortion. The purpose of feeding the I

RMS

is to reduce the loop gain at high voltages. It would otherwise become

excessive and create stability problems.

The third multiplier input is fed by a current proportional to the error amplifier output voltage. The purpose is to

smoothly change the RMS value of the sinusoidal current drawn from the AC line, to match the power demand and

maintain a good regulation of the output voltage.

Voltage error amplifier:

The IPS101 includes a voltage error amplifier with a non-inverting input connected to an internally trimmed 2.06V

reference. Its inverting input is available on pin 2. Its output is connected to pin 3 and is also internally connected to

the V-to-I converter feeding the multiplier as discussed before. As indicated in the typical application schematic of

figure 1, pin 2 and pin 3 are used for the following purposes:

(a) voltage divider R3, R4 used to set the value of the regulated DC output voltage:

DC out = 2.06 x (R3 +R4)/R4 (see Fig. 1)

(b) the loop feedback compensation network R2, C2, C6 (see Fig. 1) provides a suitable network for most

applications. More complicated schemes are possible for demanding applications where transient response is

paramount.

MOSFET current control:

The IPS101 is equivalent to a non-isolated flyback (boost) converter that operates from raw rectified AC. It uses a

high-Q inductor operating in continuous mode to generate a regulated DC output that always slightly exceeds the

peak value of the AC input voltage.

The maximum current in the inductor is set by the output of the multiplier and will increase with the output power

demand. The minimum current in the inductor is internally set to 50% of the maximum current, which constitutes a

good trade-off between energy transfer and switching losses / EMI signature at MOSFET turn-on.

When the Vcc is established, the control logic turns the MOSFET on. The current in the inductor (and also in the

MOSFET) is sensed by R9 which value along with L1 defines the power handling capacity of the PFC.

MOSF ET driver: Thermal shutdown: Shunt bandggg regulator:

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

When the current reaches the peak value set by the output voltage of the multiplier which never exceeds 1.2V, the

MOSFET is switched off and the current in the inductor, still sensed by R9, decreases as the inductive energy is

dumped into the storage capacitor. When the current decreases below 50% of the peak value, the control logic turns

the MOSFET on again. The system is therefore self-oscillating and does not require any dedicated oscillator.

Please note that the frequency varies with the load and the line voltage, but against common belief:

- its variation usually stays in a 2:1 range,

- its jitter is favorable to the EMI signature,

- it decreases when the load increases which is excellent for the efficiency of the PFC.

MOSFET driver:

The MOSFET driver has been sized to be capable of driving power MOSFETs featuring a total gate charge up to

80nC.

Due to the continuous mode of operations of the inductor, the MOSFET must be driven with a reasonably (but not

excessively) low impedance, to minimize switching losses at both turn-on and turn-off without generating too

excessive EMI.

In term of Ron, the driver’s output devices are as follow:

- P-channel Ron: 30 Ω typical

- N-channel Ron: 20 Ω typical

A series resistor R7 on pin7 should be added to further reduce EMI and minimize the noise injection which could

result from Miller-capacitance kick-back during transient conditions.

Examples of suitable MOSFETS:

- IXYS PolarHT™ and Polar HV™ MOSFET series: IXTY1R4N60P, IXTY2N60P, IXTY3N60P

- Fairchild MOSFET series: FQPF1N60, FQPF 2N60, FQPF 3N60.

- Infineon COOLMOS

TM

series: SPD01N60S5, SPD02N60S5, SPD03N60S5.

- Motorola MOSFET series: MTP1N60, MTP2N60, MTP3N60.

- SGS-Thomson MOSFET series: STD1NB60, STD2NB60, STD3NB60.

- Etc…

Notes:

- Due to the rapid evolution of MOSFET technologies, please check for current models when designing a new

SMPS.

- PolarHT™ and Polar HV™ are trademarks of IXYS corporation

COOLMOS

TM

is a trademark of Infineon.

Thermal shutdown:

An internal temperature sensing protection circuit disables the MOSFET gate drive when the temperature exceeds a

typical value of 150°C. This circuit has sufficient hysteresis to prevent relaxation. Normal operations therefore only

resume when the junction temperature has dropped below approximately 120°C.

Shunt bandgap regulator:

The IPS101 internal trimmed bandgap shunt regulator behaves like a 10V zener but also provides the 2.06V

reference for the voltage error amplifier, and the various internal bias current and voltages required by the different

blocks.

During start-up, the current consumption in the regulator is very low, typically 100μA, allowing many possible

schemes to power the IPS101. Once the “zener” value is reached, the MOSFET gate drive is enabled and normal

operation starts. When enabled, the typical chip consumption is 660 μA plus the current necessary to drive the

MOSFET which depends on the MOSFET’s total gate charge and the frequency of operation (linked to L1

inductance value).

The VCC voltage is allowed to drop below the “zener” value during normal operations but the circuit will reset itself

and re-enter start-up mode should the VCC drop below approximately 8 volts.

How to Bower the lPSlOl: Stand-alone agnlications SZ .vE :JE ' a}: HE §|§

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

The shunt regulator is sized to handle up to 50mA, which is especially useful to power the IPS101 with few

components only. Be careful however not to exceed the package rated power dissipation (see table p7).

How to power the IPS101:

There are several ways of supplying power to the IPS101 which depends on whether the PFC is used as a stand-

alone block or is followed by a DC/DC converter or other blocks using additional ICs which must be energized as

well. Stand-alone applications

Simple RC network:

The simplest technique well suited for 120V AC (domestic US and Japan) uses an RC network connected between

DC out and GND. R5 should be sized to deliver enough Icc current for normal operation without wasting power.

Figure 4

Auxilliary winding:

The most efficient technique suitable for international applications (85V- 265V AC) uses an auxillairy winding on

the switching inductor TX1. The turn-ratio between the principal winding and this auxilliary one is usually between

5 and 15. The wire size should be suitable for 20mA RMS which is quite small.

Figure 5

+

C5

L1

D1

PFC Controller

R7

R2

R6

PFC GND

C3

R3 R1

R9

C1

31

4 2

BR1

R4

AC IN

DC OUT

VCC

1

VDCFBK

2

COMPV

3

RMSCAP

4

VAC 8

DRIVE 7

ISENSE 6

GND 5

U1

IPS101

T1

CMC

C4

C2

CHIP SUPPLY

R5

+

C6

Q1

NMOSFET

+

C5

D1

PFC Controller

R7R2

R6

PFC GND

C3

R3 R1

R9

C1

31

4 2

BR1

R4

AC IN

DC OUT

VCC

1

VDCFBK

2

COMPV

3

RMSCAP

4

VAC 8

DRIVE 7

ISENSE 6

GND 5

U1

IPS101

T1

CMC

C4

C2

TX1

R5

D2

D3

C8

R8

+

C6

Vcc

C7

Q1

NMOSFET

A9211 on: WIth DC/DC converter:

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

Applications with DC/DC converter:

The auxilliary winding on L1 can be saved and the VCC supply for the the IPS101 is then provided by the DC/DC

converter circuitry. The current provided by AAI patented snubber and R9/C7 networks is divided and derived into

R13/C10 and R5/C11 to feed flyback and feedback controllers respectively.

ELECTRICAL CHARACTERISTICS

ABSOLUTE MAXIMUM RATING

Characteristics Value UNITS

Shunt regulator max I

CC

non-repetitive current (pin 1)

- see fig 7-

60 mA

Peak drive output current (pin7) Source=100, Sink=200 mA

Isense input voltage (pin 6) 0 / - 10 V

VAC maximum input current (pin8) 700 μA

Junction to case thermal resistance R

θJ-C

PDIL = 42, SOIC = 45

Junction to PCB thermal resistance R

θJ-A

PDIL = 125, SOIC =155 °C / W

Power dissipation for T

A

<= 70°C PDIL = 640, SOIC = 500 mW

Operating junction temperature - 40 to 150

Storage temperature range - 55 to 150

Lead temperature (3 mm from case for 5 sec.) 260

°C

+

C5

L1

D1

PFC Controller

R7

R2

R6

PFC/Primary GND

C3

R3 R1

R9

C1

31

4 2

BR1

R4

AC IN

VCC

1

VDCFBK

2

COMPV

3

RMSCAP

4

VAC 8

DRIVE 7

ISENSE 6

GND 5

U1

IPS101

T1

CMC

C4

C2

CHIP SUPPLY

GATE

1

ISENSE

2

VCC

3

RBIAS

4

N/C 8

GND 7

OPTO 6

N/C 5

U2

IPS10

Q2

U3

OPTO-NPN

R12

D3

1N4148

D2

1N4148

R10

R8

R11

L2

OUT+

OUT-

SecondaryGNDPrimaryGND

R9

N/C

Network

Patented

TR1

TRANSF-1P1S

+

C8

+

C9

D5

Zener

D4

Schottky

C6

Fly back Controller

DC OUT

Snubber

+

C7

+

C10

R13

+

C11

R5

Q1

NMOSFET

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

PARAMETER TEST CONDITIONS PARAMETERS UNITS

@ 25°C unless specified MIN. TYP. MAX.

Supply, bias & circuit protection

Shunt regulator voltage (V

CC

)I

CC

= 10 mA 9.7 10.0 10.3 V

Shunt regulator dynamic

resistance 1 to 30 mA 2 4 6 Ω

Shunt regulator peak

repetitive current (I

CC

)--50 mA

Start-up current (I

CC

) - 100 150 μΑ

Under voltage lock-out (V

CC

)V

CC

– 2.1 V

CC

- 1.8 V

CC

- 1.4 V

Min I

CC

to ensure continuous

operation 4A, 600V, 20 nC

MOSFET , L= 7 mH -3- mA

Thermal shutdown trip

temperature - 150 - °C

Multiplier

Maximum operating voltage

accross ISENSE resistor (R9) See note2 -1.3 -1.2 -1.1 V

COMP voltage range 0 - 3 V

VAC input current operating

range I

CC

= 1 to 10 mA

Temp = 0 to 70°C 20 - 600 μA

RMS capacitor (pin4) - 1 - μF

Error amplifier

Reference voltage I

CC

=10mA 2.01 2.06 2.10 V

Open loop gain - 85 - dB

3 dB response - 200 - Hz

Phase margin Unity gain 65 - - Degrees

Output impedance - 30 - KΩ

P & N Outputs to MOSFET gate

P gate driver saturation 10 mA (source) - 0.3 0.5 V

N gate driver saturation 10 mA (sink) - 0.2 0.35 V

Gate pull-down resistor (internal) 30 45 65 KΩ

PDRIVE Rise time (10% to

90%) 390 pF load - 100 200 ns

NDRIVE Fall time (10% to

90%) 390 pF load - 50 100 ns

Max recommanded total

external MOSFET charge --50 nC

Note1:

Electrical parameters, although guaranteed, are not all 100% tested in production.

Note2:

To avoid damage to pin 6 by the in-rush current, size R6 to limit the input current into the IC to 30mA.

1Kohm to 33Kohm are suitable values for most applications.

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

Figure 8: Vcc Drift over Temperature

10.06

10.08

10.1

10.12

10.14

10.16

10.18

10.2

-30 -10 10 30 50 70 90 110 130

Temperature (°C)

Icc (mA)

Icc=30mA

Icc=10mA

Figure 7: Shunt Regulator Icc Current

0

20

40

60

80

100

120

140

02468101214

Vcc

Icc

Figure 9: 2.06V Ref. Drift over Temperature

2.010

2.020

2.030

2.040

2.050

2.060

2.070

-40 -20 0 20 40 60 80 100 120

Temperature (°C)

Vref (Volts)

Icc=10mA

Icc=30mA

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

Figure 10: Start-Up Current Drift over Temperature

0

20

40

60

80

100

120

140

160

-30 -10 10 30 50 70 90 110

Temperature (°C)

Start-Up Icc (μA)

Figure 11: Efficiency versus Output Power

0.8

0.82

0.84

0.86

0.88

0.9

0.92

0.94

0.96

0.98

1

10 20 30 40 50 60 70 80 90 100

Output Power

Efficiency

220V IN, 420V OUT

100V IN, 420V OUT

/\/\ /\ \/W/ V VA / \/\ \ /\/\ /\

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

EXAMPLE OF POWER FACTOR CORRECTION: Universal Input, 400V DC, 100W output

Figure 12

Note:

1mH to 10mH inductors (TX1) could be used depending on conditions and targeted characteristics.

Line current waveforms: measured on IPS-DK101 demo-kit

Vin= 230V, Pout=100W

+

C5

100uF

400V

Q1

9N60

D1

FR805

PFC Controller

R7

100

R2

24K

R6

1K

PFC GND

C3

0.47uF

250V

R3

976K 1%

R1

1Meg

R9

0.5

1W

C1

1uF

31

4 2

BR1

2A 400V

R4

4.99K 1%

AC IN

DC OUT

VCC

1

VDCFBK

2

COMPV

3

RMSCAP

4

VAC 8

DRIVE 7

ISENSE 6

GND 5

U1

IPS101

C2

220nF

TX1

1.5mH

R5

100

D2

1N4148

D3

1N4148

C8

47nF

R8

750K

+

C6

47uF

Vcc

C7

100nF

D4

1N5406

P=155T, S=12T

85V - 285V AC

400V DC

100W

vm=115VACPmt=ID ‘ «5mm Pm1=5 I

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

Vin= 230V, Pout=50W

Vin= 110V, Pout=100W

V

in= 110V

,

Pout=50W

P'N‘ 8-Pin Plastic DIP 260mm) 2‘0 (5.10) .045 (1‘4) 070“ 75) .030 (0.76) 045 (1 14) .310 (7.67) .7400 (10.16) '29" (7'37) 04503.54) .2oo(5.oa) _ 1409.55) L j i 040(102) 020 (0-5‘) .015 0.33 v . .150 (3.81) f .005 (0.20) 3 MIN .115(2.92) _ _—| L- __H__ .wouom) .310 (7.07) 110(279) 022(0 56) 09012 29) 0150). as) PIN I )ndicaled by 001 and / or beveled edge 7 8 Pin-SOIC 157(199) 244 (6,20) .150 (3.81) 22815.79) .050 (1.21) TYP. 197 (5. 00)__ ll‘ﬁss (4. 30)‘ _ _ _ .069 (1.75) _L 0530.35) ”MAX _Lo10(o.25) - . . . T_ . _-| |-— 70071013) .010 (0.46) .010 (0.25) 050 1 27 01403.36) ,004 (0.10) :016 $0.40}

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

PACKAGE DIMENSIONS

PLASTIC DIP-8

PLASTIC SOIC-8

Examgle of Marking Note n—uu—un—un—u ._.._.._.._. NoteW Note2 Nole u—n—uu—un—u

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

ORDERING INFORMATION

Part-Number

Example of Marking

(Note : For production with a new date code, since January 2006, the package type does not appear anymore on package

marking)

This ordering information is for commercial and industrial standard IN-PLUG® controllers ONLY. For custom controllers or for

military temperature range, call AAI’s sales representative.

IN-PLUG® Controller Series

Flyback

Feedback

PFC

Push-Pull

LED Driver

Controller Type

Flyback: 10 series

Feedback: 20 series

PFC: 100 series

Push-Pull: 200 series

Automotive: 300 series

LED Driver: 400 series

“H” with hiccup overload

protection

ROHS + Pb-Free

Tape and Reel

TR : Tape & Reel

TU : Tube

Note1 : Default or not specified

is « tube ».

Note2 : Does not appear on

package marking.

Temperature Range

C : Commercial (0, +70°C)

I : Industrial (-40°C. +85°C)

A: Automotive (-40°C. +125°C)

Note : Default or not specified is <commercial>

Package Type

D : DIP8

SO : SOIC8

(For production with a new date code, since January

2006, the package type does not appear anymore on

package marking)

IPS XXXH C – YY – G-LF - TR

Non-Green Package Green ROHS + Pb-Free Package

AAI

IPS15HC

YYWW

AAI G-LF

IPS15HC

YYWW

LIMITED WARRANTY CRITICAL APPLICATIONS LETHAL VOLTAGES INTELLECTUAL PROPERTY RIGHTS AND PROPRIETARY DATA TRADEMARKS AND PATENTS PROTECTION FOR CUSTOM lN-PLUG® SOLUTIONS COMPLIANCE WITH LAWS TITLE AND DELIVERY LATEST DATASHEET UPDATES WORLDWIDE REPRESENTATIVES COPYRIGHTS

IN-PLUG

®

I

IP

PS

S1

10

01

1

Datasheet – Rev.10 - High Efficiency Power Factor Correction C

Co

on

nt

tr

ro

ol

ll

le

er

r

The following is a brief overview of certain terms and conditions of sale of product. For a full and complete copy of all

the General Terms and Conditions of Sale, visit our webpage http://www.asicadvantage.com/terms.htm.

LIMITED WARRANTY

The product is warranted that it will conform to the applicable specifications and be free of defects for one year.

Buyer is responsible for selection of, use of and results obtained from use of the product. Buyer indemnifies and

holds ASIC Advantage, Inc. harmless for claims arising out of the application of ASIC Advantage, Inc.’s products to

Buyer’s designs. Applications described herein or in any catalogs, advertisements or other documents are for

illustrative purposes only.

CRITICAL APPLICATIONS

Products are not authorized for use in critical applications including aerospace and life support applications. Use of

products in these applications is fully at the risk of the Buyer. Critical applications include any system or device

whose failure to perform can result in significant injury to the user.

LETHAL VOLTAGES

Lethal voltages could be present in the applications. Please comply with all applicable safety regulations.

INTELLECTUAL PROPERTY RIGHTS AND PROPRIETARY DATA

ASIC Advantage, Inc. retains all intellectual property rights in the products. Sale of products does not confer on Buyer

any license to the intellectual property. ASIC Advantage, Inc. reserves the right to make changes without notice to

the products at any time. Buyer agrees not to use or disclose ASIC Advantage Inc.’s proprietary information without

written consent.

TRADEMARKS AND PATENTS

- IN-PLUG® is a registered trademark of ASIC Advantage, Inc.

- AAI’s modified snubber network is patented under the US Patent # 6,233,165. IN-PLUG® Customers are granted

a royalty-free licence for its utilization, provision the parts are purchased factory direct or from an authorized agent.

PROTECTION FOR CUSTOM IN-PLUG® SOLUTIONS

When AAI accepts to design and manufacture IN-PLUG® products to Buyer’s designs or specifications, buyer has

certain obligations to provide defense in a suit or proceeding claiming infringement of a patent, copyright or trademark

or for misappropriation of use of any trade secrets or for unfair competition.

COMPLIANCE WITH LAWS

Buyer agrees that at all times it will comply with all applicable federal, state, municipal, and local laws, orders and

regulations. Buyer agrees to comply with all applicable restrictions on exports and re-exports including obtaining any

required U.S. Government license, authorization, or approval. Buyer shall pay any duties, levies, taxes, brokerage

fees, or customs fees imposed on the products.

TITLE AND DELIVERY

All shipments of goods shall be delivered ExWorks, Sunnyvale, CA, U.S.A. Title in the goods shall not pass to Buyer

until ASIC Advantage, Inc. has received in full all amounts owed by Buyer.

LATEST DATASHEET UPDATES

For the latest datasheet updates, visit our web page: http://www.in-plug.com/datasheets.htm.

WORLDWIDE REPRESENTATIVES

To access AAI’s list of worldwide representatives , visit our web page http://www.in-plug.com/representatives.htm

COPYRIGHTS

Copyrights and all other proprietary rights in the Content rests with ASIC Advantage Inc. (AAI) or its licensors. All

rights in the Content not expressly granted herein are reserved. Except as otherwise provided, the Content published

on this document may be reproduced or distributed in unmodified form for personal non-commercial use only. Any

other use of the Content, including without limitation distribution, reproduction, modification, display or transmission

without the prior written consent of AAI is strictly prohibited. All copyright and other proprietary notices shall be

retained on all reproductions. ASIC Advantage INC.

1290-B Reamwood Ave, Sunnyvale California 94089, USA

Tel: (1) 408-541-8686 Fax: (1) 408-541-8675

Websites: http://www.in-plug.com - http://www.asicadvantage.com

IPS101 Datasheet by Microsemi PoE Ltd.

Products related to this Datasheet