MP2161A Datasheet by Monolithic Power Systems Inc.

Efﬁciency V‘N=v.vom=3.3v mo u \ ’VVV‘ ' o A so i * y. L) “I g I ~ a 8° : Q 0 : t 70 m an n so 1 10 we was moon LOAD CURRENTUHA)

MP2161A

2A, 6V, 1.5MHz, 17μA IQ, COT

Synchronous Step-Down Converter

in 8-pin TSOT23

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The Future of Analog IC Technology

DESCRIPTION

The MP2161A is a monolithic, step-down,

switch-mode converter with built-in internal

power MOSFETs. It achieves a 2A continuous

output current from a 2.5V to 6V input voltage

range with excellent load and line regulation.

The output voltage is regulated as low as 0.6V.

The constant-on-time (COT) control scheme

provides fast transient response and eases loop

stabilization. Fault condition protection includes

cycle-by-cycle current limiting and thermal

shutdown.

The MP2161A is available in a small TSOT23-8

package and requires a minimum number of

readily available, standard, external

components.

The MP2161A is ideal for a wide range of

applications including high performance DSPs,

FPGAs, PDAs, and portable instruments.

FEATURES

 Very Low IQ: 17A

 Default 1.5MHz Switching Frequency

 1.5% VFB Accuracy

 EN and Power Good for Power Sequencing

 Wide 2.5V to 6V Operating Input Range

 Output Adjustable from 0.6V

 Up to 2A Output Current

 100% Duty Cycle in Dropout

 110m and 60m Internal Power MOSFET

Switches

 Cycle-by-Cycle Over-Current Protection

 Short-Circuit Protection with Hiccup Mode

 Stable with Low ESR Output Ceramic

Capacitors

 Available in a TSOT23-8 Package

APPLICATIONS

 Wireless/Networking Cards

 Portable Instruments

 Battery Powered Devices

 Low Voltage I/O System Power

All MPS parts are lead-free, halogen-free, and adhere to the RoHS directive.

For MPS green status, please visit the MPS website under Quality Assurance.

“MPS” and “The Future of Analog IC Technology” are registered trademarks of

Monolithic Power Systems, Inc.

TYPICAL APPLICATION

MP2161A

AGND PGND

FB

VIN

C1

10 F

EN

VIN

2.5V to 6V

VOUT

1.2V/ 2A

SW

C2

10 F

R1

200k

R2

200k

PG

EN

PG

OUT

L1

1H

l'l'll'j’ IAKRY

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ORDERING INFORMATION

Part Number* Package Top Marking

MP2161AGJ TSOT23-8 See Below

* For Tape & Reel, add suffix –Z (e.g. MP2161AGJ–Z)

TOP MARKING

AKR: Product code of MP2161AGJ

Y: Year code

PACKAGE REFERENCE

PG

VIN

SW

PGND

EN

FB

AGND

OUT

1

2

3

4

8

7

6

5

TOP VIEW

TSOT23-8

MIPS TJ

MP2161A – 2A, 6V, 1.5MHz SYNCHRONOUS STEP-DOWN CONVERTER

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ABSOLUTE MAXIMUM RATINGS (1)

Supply voltage (VIN) .................................... 6.5V

VSW ......................................................................

-0.3V (-1.5V for <20ns&-4V for <8ns) to 6.5V

(10V for <10ns)

All other pins .................................-0.3V to 6.5 V

Junction temperature ................................150C

Lead temperature .....................................260C

Continuous power dissipation (TA = +25°C) (2)

……….….. ............................................... 1.25W

Storage temperature................ -65C to +150C

Recommended Operating Conditions (3)

Supply voltage (VIN) ...........................2.5V to 6V

Operating junction temp. (TJ). .. -40°C to +125°C

Thermal Resistance (4) θJA θJC

TSOT23-8.............................. 100 ..... 55... C/W

NOTES:

1) Exceeding these ratings may damage the device.

2) The maximum allowable power dissipation is a function of the

maximum junction temperature TJ (MAX), the junction-to-

ambient thermal resistance JA, and the ambient temperature

TA. The maximum allowable continuous power dissipation at

any ambient temperature is calculated by PD (MAX) = (TJ

(MAX)-TA)/JA. Exceeding the maximum allowable powe

r

dissipation will produce an excessive die temperature,

causing the regulator to go into thermal shutdown. Internal

thermal shutdown circuitry protects the device from

permanent damage.

3) The device is not guaranteed to function outside of its

operating conditions.

4) Measured on JESD51-7, 4-layer PCB.

““35” (a)

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ELECTRICAL CHARACTERISTICS

VIN = 5V, TA = +25C, unless otherwise noted.

Parameter Symbol Condition Min Typ Max Units

2.5V ≤ VIN ≤ 6V, TA =

25oC -1.5 0.600 +1.5

Feedback voltage VFB

TA = -40oC to +85oC (6) -2.5 +2.5

V/%

Feedback current IFB V

FB = 0.6V 10 50 nA

PFET switch on resistance RDSON_P 110 m

NFET switch on resistance RDSON_N 60 m

Switch leakage VEN = 0V, VIN = 6V

VSW = 0V and 6V 0 1 A

PFET current limit 2.6 3.2 4.0 A

VIN = 5V, VOUT = 1.2V 166

On time TON VIN = 3.6V, VOUT = 1.2V 220 ns

VOUT = 1.2V, TA = 25oC -20 1500 +20 kHz/%

Switching frequency Fs TA = -40oC to +85oC(6) -25 1500 +25 kHz/%

Minimum off time(6) T

MIN-OFF 60 ns

Soft-start time TSS-ON V

OUT from 10% to 90% 0.6 1.15 1.7 ms

Power good upper trip threshold PGH FB voltage respect to the

regulation +10 %

Power good lower trip threshold PGL -10 %

Power good delay PGD 50 s

Power good sink current capability VPG-L Sink 1mA 0.4 V

Power good logic-high voltage VPG-H V

IN = 5V, VFB = 0.6V 4.9 V

Power good internal pull-up

resistor RPG 550 k

Under-voltage lockout threshold—

rising 2.15 2.3 2.45 V

Under-voltage lockout threshold—

hysteresis 260 mV

EN input logic-low voltage 0.4 V

EN input logic-high voltage 1.2 V

VEN = 2V 1.5 A

EN input current VEN = 0V 0 A

Supply current (shutdown) VEN = 0V, VIN = 3V 20 100 nA

Supply current (quiescent) VEN = 2V, VFB = 0.63V,

VIN = 5V 17 20 A

Thermal shutdown(5) 150

C

Thermal hysteresis(5) 30

C

NOTES:

5) Guaranteed by design.

6) Guaranteed by characterization test.

HIPS’ LlNE REGULATlON(%) CURRENTwA) EFFIClENCV(%) Quiescent Current vs. Shutdown Current vs. Input Voltage Input Voltage 40 0 003 0 0025 30 2 3 0 002 F E 20 [I 0 0015 m 3 0.001 10 o 0005 0 0 2 25 3 35 4 4.5 5 556 2 2.5 3 3.5 4 4.5 5 5.5 6 lNPUTVOLTAGE (V) lNPUT VOLTAGE (V) Line Regulation Case Temperature Rise VlN:3V. VOUT:1 2v 0.2 50 0 15 45 a 40 0.1 I 35 0.05 § 30 ° lowm E 25 70 05 E 20 “J 15 w '0 1 lour=2A 8 m -0.15 5 70.2 0 2.5 3 35 A 45 5 5.5 s 0 0.5 1 15 2 2.5 lNFUT VOLTAGE (V) OUTPUT CURRENT (A) Efficiency Efficiency 5v/3.3v VW.1.8V VDUT 100 100 95 W=3 av 90 90 K- 55 E \ , 30 g 30* v‘ :5v ,7 vw:3 3v * 75 E 70 E 70 65 m 60 60 55 50 50 1 10 100 1000 10000 0 05 1 15 2 25 LOAD CURRENT(mA) low (A) LOAD REGULATlON (% CASE TEMP RISE (“C) EFFlClENCY(°/a) Load Regulation 0 10 0 06 0.06 0.04 0 D2 0 00 -0.02 70.04 70 06 -o as -0.10 00 0.5 1.0 15 LOAD C URRE NT (A) 2.0 Case Temperature Rise VlN:5V. VOUT:3 3V Aummwbbw momomcmo 0010 0 0.5 1 15 2 OUTPUT CURRENT (A) 2.5 Efficiency 5v le. 3.3V VOW 100 m o on o ‘4 o as o w o 0 u 5 1 low (A) 15 2 25

MP2161A – 2A, 6V, 1.5MHz SYNCHRONOUS STEP-DOWN CONVERTER

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TYPICAL PERFORMANCE CHARACTERISTICS

VIN = 5V, VOUT = 1.2V, L = 1.0µH, TA = +25ºC, unless otherwise noted.

l'l'IPj’ Reference Voltage vs. Temperature 650 640 630 620 610 600 590 580 570 560 550 750 0 50 l 00 1 50 TEMPERATURE (“C) REFERENCE VOLTAGE (mV)

MP2161A – 2A, 6V, 1.5MHz SYNCHRONOUS STEP-DOWN CONVERTER

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TYPICAL PERFORMANCE CHARACTERISTICS (continued)

VIN = 5V, VOUT = 1.2V, L = 1.0µH, TA = +25ºC, unless otherwise noted.

ll'll'j’ Output Ripple Output Ripple Output Ripple ‘auT:0A IOWA 5sz V we / Vow/AC WM VOW/AC WWW qu/aw" lomv/cwmv W V lomvmwp 'l ‘ 1 1 r1 v v 5‘ng all mam... . .__l 5V,§‘C{m...i b. J34 .. JL numb , M WM 7 zm‘L IL w his/div Aoons/dw 2N“ wens/div V|_N Power-Up VIN Power-Up VIN Shutdown wﬂhout Load with 2A Load without Load W L IV/dlv ﬁ) “ ViN L 2V/dlv __ V will“ ' i WmL ﬁ 2ms/div ZOUmS/dlv VIN Shutdown EN Start-Up EN Start-Up with 2A Load without Load with 2A Load 3 ‘ a ‘ ‘ ‘ ‘ a M w...— Vom W“ V V M ‘V’G‘V m \N My; ' 1vﬁ1ligﬁ‘ \ V V V 2mm?) W SV/dEid 3‘ 5V/dEl‘y V v ~~v- v will" swﬁ’ ’ will“ ” ‘L l 4M» i W" " wan} ‘ lA/dIvL W Ams/mv 2ms/dw.

MP2161A – 2A, 6V, 1.5MHz SYNCHRONOUS STEP-DOWN CONVERTER

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TYPICAL PERFORMANCE CHARACTERISTICS (continued)

VIN = 5V, VOUT = 1.2V, L = 1.0µH, TA = +25ºC, unless otherwise noted.

"IFS EN Shutdown EN Shutdown without Load with 2A Load i1 VDW V ‘5...“ 1V/dw m wﬂ,‘ m VEN vEN 5V/dw 5“];le VSW V 5V/div w 2min: " IL A lA/dw. D ‘L mums/aw Wd” mus/aw

MP2161A – 2A, 6V, 1.5MHz SYNCHRONOUS STEP-DOWN CONVERTER

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TYPICAL PERFORMANCE CHARACTERISTICS (continued)

VIN = 5V, VOUT = 1.2V, L = 1.0µH, TA = +25ºC, unless otherwise noted

l'l'll'j’

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PIN FUNCTIONS

Pin # Name Description

1 PG

Power good indicator. The output of PG is an open drain with an internal pull-up resistor

to VIN. PG is pulled up to VIN when the FB voltage is within ±10% of the regulation level.

If FB voltage is out of that regulation range, it is low.

2 VIN

Supply voltage. The MP2161A operates from a +2.5V to +6V unregulated input. C1 is

needed to prevent large voltage spikes from appearing at the input.

3 SW

Switch output.

4 PGND

Power ground.

5 OUT

Input sense for output voltage.

6 AGND

Analogy ground for internal control circuit.

7 FB

Feedback. An external resistor divider from the output to AGND (tapped to FB) sets the

output voltage.

8 EN

On/off control.

"It l'l'll'j’

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FUNCTIONAL BLOCK DIAGRAM

Main

Switch

(PCH)

Synchronous

Rectifier

(NCH)

Constant

On -Time

Pulse

PWM

Bias

&

Voltage

Reference

0.6 V

EN

FB

SW

COMP

+

-

VIN

+

-

FBCOMP EN

Driver

PDRV

NDRV

Soft start

PGND

AGND

OUT

PWM

COMP

+

-

COMP

+

-

0. 66 V

0. 54 V

PG

Hi-Z

FB for

Fixed Output

VIN

E.A.

+

-

+

Ramp

Generator

COMP

+

-

VOUT

RST

SW

Lo - Iq

Lo-Iq

V

TH

Figure 1: MP2161A Block Diagram

MIPS’

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OPERATION

The MP2161A uses constant-on-time (COT)

control with input voltage feed forward to stabilize

the switching frequency over the full input range.

At light load, the MP2161A employs a proprietary

control of the low-side switch and inductor

current to eliminate ringing on the switching node

and improve efficiency.

Constant-On-time (COT) Control

Compared to fixed frequency PWM control,

constant-on-time (COT) control offers the

advantage of a simpler control loop and faster

transient response. By using input voltage feed

forward, the MP2161A maintains a nearly

constant switching frequency across the input

and output voltage range. The on time of the

switching pulse is estimated with Equation (1):

OUT

ON

IN

V

T0.667s

V



(1)

To prevent inductor current runaway during load

transient, the MP2161A fixes the minimum off

time at 60ns. However, this minimum off time

limit will not affect operation of the MP2161A in

steady state.

Light-Load Operation

In a light-load condition, the MP2161A uses a

proprietary control scheme to save power and

improve efficiency. The MP2161A turns off the

low-side switch when the inductor current starts

to reverse. Then the MP2161A works in

discontinuous conduction mode (DCM) operation.

There is a zero current cross circuit to detect if

the inductor current starts to reverse.

Considering the internal circuit propagation time,

the typical delay is 50ns. This means that with

this delay the inductor current will still fall after

the ZCD is triggered. If the inductor current falling

slew rate is fast (Vo voltage is high or close to

Vin), the low-side MOSFET (LS-FET) is turned

off, and the inductor current may be negative.

This phenomenon prevents the MP2161A from

entering DCM operation, even with no load. If

DCM mode is required, the off time of the LS-

FET in CCM should be longer than 100ns (2

times the propagation delay). For example, if Vin

is 3.6V and Vo is 3.3V, the off time in CCM is

55ns. It is difficult to enter DCM at light load.

Using a smaller inductor can improve this

condition and make it easier to enter DCM.

Enable (EN)

When the input voltage is greater than the under-

voltage lockout threshold (UVLO), typically 2.3V,

the MP2161A is enabled by pulling EN higher

than 1.2V. Floating or pulling EN down to ground

disables the MP2161A. There is an internal 1M

resistor from EN to ground.

Soft Start (SS)

MP2161A has built-in soft start that ramps up the

output voltage in a controlled slew rate, avoiding

overshoot at start-up. The soft-start time is about

1.15ms typically.

Power GOOD Indicator

MP2161A has an open drain with a 550k pull-

up resistor pin for a power good indicator (PG).

When FB is within +/-10% of the regulation

voltage (e.g., 0.6V), PG is pulled up to VIN by the

internal resistor. If the FB voltage is out of the +/-

10% window, PG is pulled down to ground by an

internal MOSFET. The MOSFET has a maximum

Rdson of less than 400.

Current Limit

MP2161A has a typical 3.2A current limit for the

high-side switch. When the high-side switch hits

the current limit, the MP2161A reaches the

hiccup threshold until the current decreases. This

prevents the inductor current from continuing to

build up, which results in damage to the

components.

Short Circuit and Recovery

The MP2161A enters short-circuit protection

mode when the current limit is reached. It tries to

recover from the short circuit with hiccup mode.

In short-circuit protection, the MP2161A disables

the output power stage, discharges a soft-start

capacitor, and then automatically tries to soft

start again. If the short-circuit condition remains

after the soft start ends, the MP2161A repeats

this operation cycle until the short circuit

disappears, and the output rises back to

regulation level.

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APPLICATION INFORMATION

COMPONENT SELECTION

Setting the Output Voltage

An external resistor divider is used to set the

output voltage (see Typical Application on page

1). The feedback resistor R1 cannot be too

large or too small considering the trade-off

between a dynamic circuit and stability in the

circuit. Choose R1 around 120k to 200k. R2

is then given using Equation (2):

out

R1

R2 V1

0.6





(2)

The feedback circuit is shown in Figure 2.

R1

R2

Vout

FB

MP2161A

Figure 2: Feedback Network

Table 1 lists the recommended resistor values

for common output voltages.

Table 1—Resistor Selection for Common Output

Voltages

VOUT (V) R1 (kΩ) R2 (kΩ)

1.0 200(1%) 300(1%)

1.2 200(1%) 200(1%)

1.8 200(1%) 100(1%)

2.5 200(1%) 63.2(1%)

3.3 200(1%) 44.2(1%)

Selecting the Inductor

A 0.68µH to 2.2µH inductor is recommended for

most applications. For highest efficiency, the

inductor DC resistance should be less than

15m. For most designs, the inductance value

can be derived from Equation (3):

OUT IN OUT

1

IN L OSC

V(VV)

LVIf



  (3)

Where IL is the inductor ripple current.

Choose the inductor current to be

approximately 30% of the maximum load

current. The maximum inductor peak current is

calculated using Equation (4):

2

I

II L

LOAD)MAX(L



 (4)

Selecting the Input Capacitor

The input current to the step-down converter is

discontinuous, therefore a capacitor is required

to supply the AC current to the step-down

converter while maintaining the DC input

voltage. Use low ESR capacitors for the best

performance. Ceramic capacitors with X5R or

X7R dielectrics are highly recommended

because of their low ESR and small

temperature coefficients. For most applications,

a 10µF capacitor is sufficient. For a higher

output voltage, a 47µF capacitor may be

needed for a more stable system.

Since the input capacitor absorbs the input

switching current, it requires an adequate ripple

current rating. The RMS current in the input

capacitor can be estimated with Equation (5)

and Equation (6):















IN

OUT

IN

OUT

LOAD1C V

V

1

V

II (5)

The worse case condition occurs at VIN = 2VOUT,

where:

2

I

ILOAD

1C  (6)

For simplification, choose an input capacitor

with an RMS current rating greater than half of

the maximum load current.

The input capacitor can be electrolytic, tantalum,

or ceramic. When using electrolytic or tantalum

capacitors, a small, high-quality ceramic

capacitor (e.g., 0.1F) should be placed as

close to the IC as possible. When using

ceramic capacitors, make sure they have

enough capacitance to provide sufficient charge

to prevent excessive voltage ripple at the input.

The input voltage ripple caused by capacitance

can be estimated with Equation (7):

LOAD OUT OUT

IN IN

SIN

IV V

V1

fC1V V



  





(7)

l'I'IPj’ aaélé if”

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Selecting the Output Capacitor

The output capacitor (C2) is required to

maintain the DC output voltage. Ceramic

capacitors are recommended. Low ESR

capacitors are preferred to keep the output

voltage ripple low. The output voltage ripple can

be estimated with Equation (8):

OUT OUT

OUT ESR

S1 IN S

VV 1

V1R

fL V 8fC2



   







(8)

Where L1 is the inductor value and RESR is the

equivalent series resistance (ESR) value of the

output capacitor.

When using ceramic capacitors, the impedance

at the switching frequency is dominated by the

capacitance. The output voltage ripple is

caused mainly by the capacitance. For

simplification, the output voltage ripple can be

estimated with Equation (9):

OUT OUT

OUT 2

IN

S1

VV

V1

V

8f L C2







 

(9)

When using tantalum or electrolytic capacitors,

the ESR dominates the impedance at the

switching frequency. For simplification, the

output ripple can be approximated with

Equation (10):

OUT OUT

OUT ESR

IN

S1

VV

V1R

fL V









(10)

The characteristics of the output capacitor

affect the stability of the regulation system.

PCB Layout Guidelines

Efficient PCB layout of the switching power

supplies is critical for proper IC function. A poor

layout design can result in poor line or load

regulation and stability issues. For best results,

please refer to Figure 3 and follow the

guidelines below:

1. Place the high current paths (GND, VIN,

and SW) very close to the device with

short, direct, and wide traces.

2. Place the input capacitor as close as

possible to the VIN and GND pins.

3. Place the external feedback resistors

next to FB.

4. Keep the switching node (SW) short and

away from the feedback network.

8

7

6

5

L1

C2

C2A

R1

R4

R3

R2

1

2

3

4

OUT

VIN

GND

SW

C1C1A

Figure 3: Recommended PCB Layout

Design Example

Table 2 is a design example following the

application guidelines for the specifications:

Table 2: Design Example

VIN 5V

VOUT 1.2V

fSW 1500kHz

The detailed application schematic is shown in

Figure 4. The typical performance and circuit

waveforms have been shown in the “Typical

Performance Characteristics” section. For more

device applications, please refer to the related

evaluation board datasheets.

l'l'IPj’ H-

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TYPICAL APPLICATION CIRCUITS

MP2161A

AGND PGND

FB

VIN

C1

10 F

EN

VIN

2.5V to 6V

VOUT

1.2V/ 2A

SW

C2

10 F

R1

200k

R2

200k

PG

EN

PG

OUT

L1

1H

Figure 4: Typical Application Circuit

l'l'll'j’ AAAAAAAAA EEEEEEEEEEEEEEEEEEEEEE

MP2161A – 2A, 6V, 1.5MHz SYNCHRONOUS STEP-DOWN CONVERTER

NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.

Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS

products into any application. MPS will not assume any legal responsibility for any said applications.

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PACKAGE INFORMATION

TSOT23-8

FRONT VIEW

NOTE:

1) ALL DIMENSIONS ARE IN MILLIMETERS.

2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH,

PROTRUSION OR GATE BURR.

3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD

FLASH OR PROTRUSION.

4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER

FORMING) SHALL BE 0.10 MILLIMETERS MAX.

5) JEDEC REFERENCE IS MO-193, VARIATION BA.

6) DRAWING IS NOT TO SCALE.

7) PIN 1 IS LOWER LEFT PIN WHEN READING TOP MARK

FROM LEFT TO RIGHT, (SEE EXAMPLE TOP MARK)

TOP VIEW RECOMMENDED LAND PATTERN

SEATING PLANE

SIDE VIEW

DETAIL ''A''

SEE DETAIL ''A''

IAAAA

PIN 1 ID

See note 7

EXAMPLE

TOP MARK

MP2161A Datasheet by Monolithic Power Systems Inc.

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